LTC3416 Ver la hoja de datos (PDF) - Linear Technology

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Fabricante

LTC3416

4A, 4MHz, Monolithic Synchronous Step-Down Regulator with Tracking

Linear Technology 

LTC3416

APPLICATIO S I FOR ATIO

The basic LTC3416 application circuit is shown in Figure␣ 1a.

External component selection is determined by the maxi-

mum load current and begins with the selection of the

operating frequency and inductor value followed by CIN

and COUT.

Operating Frequency

Selection of the operating frequency is a tradeoff between

efficiency and component size. High frequency operation

allows the use of smaller inductor and capacitor values.

Operation at lower frequencies improves efficiency by

reducing internal gate charge losses but requires larger

inductance values and/or capacitance to maintain low

output ripple voltage.

The operating frequency of the LTC3416 is determined by

an external resistor that is connected between the RT pin

and ground. The value of the resistor sets the ramp current

that is used to charge and discharge an internal timing

capacitor within the oscillator and can be calculated by

using the following equation:

ROSC

=

3.08

•

f

1011

(Ω)

–

10kΩ

Although frequencies as high as 4MHz are possible, the

minimum on-time of the LTC3416 imposes a minimum

limit on the operating duty cycle. The minimum on-time is

typically 110ns. Therefore, the minimum duty cycle is

equal to 100 • 110ns • f(Hz).

Inductor Selection

For a given input and output voltage, the inductor value

and operating frequency determine the ripple current. The

ripple current ∆IL increases with higher VIN or lower VOUT

and decreases with higher inductance.

∆IL

=



VOUT

fL







1–

VOUT

VIN





Having a lower ripple current reduces the core losses in

the inductor, the ESR losses in the output capacitors and

the output voltage ripple. Highest efficiency operation is

achieved at low frequency with small ripple current. This,

however, requires a large inductor.

A reasonable starting point for selecting the ripple current

is ∆IL = 0.4(IMAX). The largest ripple current occurs at the

highest VIN. To guarantee that the ripple current stays

below a specified maximum, the inductor value should be

chosen according to the following equation:

L

=





VOUT

f∆IL(MAX)



 1–

VOUT

VIN(MAX)





Inductor Core Selection

Once the value for L is known, the type of inductor must be

selected. Actual core loss is independent of core size for a

fixed inductor value, but it is very dependent on the

inductance selected. As the inductance increases, core

losses decrease. Unfortunately, increased inductance re-

quires more turns of wire and therefore copper losses will

increase.

Ferrite designs have very low core losses and are preferred

at high switching frequencies, so design goals can con-

centrate on copper loss and preventing saturation. Ferrite

core material saturates “hard,” which means that induc-

tance collapses abruptly when the peak design current is

exceeded. This results in an abrupt increase in inductor

ripple current and consequent output voltage ripple. Do

not allow the core to saturate!

Different core materials and shapes will change the size/

current and price/current relationship of an inductor.

Toroid or shielded pot cores in ferrite or permalloy mate-

rials are small and don’t radiate much energy, but gener-

ally cost more than powdered iron core inductors with

similar characteristics. The choice of which style inductor

to use mainly depends on the price vs size requirements

and any radiated field/EMI requirements. New designs for

surface mount inductors are available from Coiltronics,

Coilcraft, Toko and Sumida.

CIN and COUT Selection

The input capacitance, CIN, is needed to filter the trapezoi-

dal wave current at the source of the top MOSFET. To

3416f

8

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