LTC4252-1IMS8-TRPBF Ver la hoja de datos (PDF) - Linear Technology

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Fabricante

LTC4252-1IMS8-TRPBF

Negative Voltage Hot Swap Controllers

Linear Technology 

LTC4252-1/LTC4252-2

LTC4252A-1/LTC4252A-2

APPLICATIONS INFORMATION

60

NTY100N10

50

40

30

20 IRF540S

IRF3710

10

0

0

IRF530S

IRF740

2000

4000

6000

MOSFET CISS (pF)

8000

425212 F07

Figure 7. Recommended Compensation

Capacitor CC vs MOSFET CISS

As seen in Figure 6 previously, at the onset of a short-

circuit event, the input supply voltage can ring dramatically

owing to series inductance. If this voltage avalanches the

MOSFET, current continues to flow through the MOSFET

to the output. The analog current limit loop cannot control

this current flow and therefore the loop undershoots. This

effect cannot be eliminated by frequency compensation. A

zener diode is required to clamp the input supply voltage

and prevent MOSFET avalanche.

SENSE RESISTOR CONSIDERATIONS

For proper circuit breaker operation, Kelvin-sense PCB con-

nections between the sense resistor and the LTC4252’s VEE

and SENSE pins are strongly recommended. The drawing in

Figure 8 illustrates the correct way of making connections

between the LTC4252 and the sense resistor. PCB layout

should be balanced and symmetrical to minimize wiring

errors. In addition, the PCB layout for the sense resistor

should include good thermal management techniques for

optimal sense resistor power dissipation.

TIMING WAVEFORMS

System Power-Up

Figure 9 details the timing waveforms for a typical power-

up sequence in the case where a board is already installed

in the backplane and system power is applied abruptly. At

CURRENT FLOW

FROM LOAD

CURRENT FLOW

TO –48V BACKPLANE

TRACK WIDTH W:

0.03" PER AMP W

ON 1 OZ COPPER

SENSE RESISTOR

425212 F08

TO

TO

SENSE

VEE

Figure 8. Making PCB Connections to the Sense Resistor

time point 1, the supply ramps up, together with UV/OV,

VOUT and DRAIN. VIN and PWRGD follow at a slower rate

as set by the VIN bypass capacitor. At time point 2, VIN

exceeds VLKO and the internal logic checks for UV > VUVHI,

OV < VOVLO, GATE < VGATEL, SENSE < VCB, SS < 20 • VOS

and TIMER < VTMRL. If all conditions are met, an initial

timing cycle starts and the TIMER capacitor is charged

by a 5.8μA current source pull-up. At time point 3, TIMER

reaches the VTMRH threshold and the initial timing cycle

terminates. The TIMER capacitor is quickly discharged. At

time point 4, the VTMRL threshold is reached and the condi-

tions of GATE < VGATEL, SENSE < VCB and SS < 20 • VOS

must be satisfied before a GATE ramp-up cycle begins.

SS ramps up as dictated by RSS • CSS (as in Equation 6);

GATE is held low by the analog current limit (ACL) ampli-

fier until SS crosses 20 • VOS. Upon releasing GATE, 58μA

sources into the external MOSFET gate and compensation

network. When the GATE voltage reaches the MOSFET’s

threshold, current begins flowing into the load capacitor

at time point 5. At time point 6, load current reaches the

SS control level and the analog current limit loop activates.

Between time points 6 and 8, the GATE voltage is servoed,

the SENSE voltage is regulated at VACL(t) (Equation 7) and

soft-start limits the slew rate of the load current. If the

SENSE voltage (VSENSE – VEE) reaches the VCB threshold

at time point 7, the circuit breaker TIMER activates. The

TIMER capacitor, CT, is charged by a (230μA + 8 • IDRN)

current pull-up. As the load capacitor nears full charge,

load current begins to decline.

425212fd

21

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